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# Surface acoustic wave photonic devices in silicon on insulator

## Abstract

Opto-mechanical interactions in planar photonic integrated circuits draw great interest in basic research and applications. However, opto-mechanics is practically absent in the most technologically significant photonics platform: silicon on insulator. Previous demonstrations required the under-etching and suspension of silicon structures. Here we present surface acoustic wave-photonic devices in silicon on insulator, up to 8 GHz frequency. Surface waves are launched through absorption of modulated pump light in metallic gratings and thermo-elastic expansion. The surface waves are detected through photo-elastic modulation of an optical probe in standard race-track resonators. Devices do not involve piezo-electric actuation, suspension of waveguides or hybrid material integration. Wavelength conversion of incident microwave signals and acoustic true time delays up to 40 ns are demonstrated on-chip. Lastly, discrete-time microwave-photonic filters with up to six taps and 20 MHz-wide passbands are realized using acoustic delays. The concept is suitable for integrated microwave-photonics signal processing.

## Introduction

The research field of opto-mechanics addresses the interaction between light and elastic waves in a common medium1,2,3,4. The topic draws great interest in recent years, in basic research of light-matter interactions and quantum mechanics, development of quantum technologies, sensing and signal processing applications. Planar photonic integrated circuits provide an excellent platform for the study of opto-mechanics, with large freedom of design, small footprint, repeatable fabrication, and integration alongside electronic and optical functionalities. Optical waves and gigahertz-frequencies acoustic waves may be coupled effectively in integrated circuits, due to the similarity in their wavelengths (for a recent comprehensive review see ref. 1). Opto-mechanical interactions are therefore suitable for the processing of signals at microwave frequencies1,5,6. Coupling between light and mechanical waves in planar integrated circuits was successfully demonstrated based on piezo-electric transduction in gallium-arsenide (GaAs) and aluminium-nitride (AlN)7,8,9,10,11,12,13,14, and optical forces in diamond15,16, silica17,18, silicon-nitride (SiN) in silica19 and chalcogenide glasses5,20,21,22,23,24.

Silicon on insulator (SOI) is arguably the most significant material platform for photonics, due to the promise of monolithic integration alongside electronic circuits25,26,27. However, opto-mechanical interactions are yet to be introduced to standard SOI photonics. Silicon does not exhibit a piezo-electric effect. In addition, the silicon device layer in SOI does not effectively guide acoustic modes, which tend to leak towards the bulk28. Remarkable demonstrations of forward stimulated Brillouin scattering in silicon have been reported in recent years29,30,31,32. However, these required that the underlying oxide layer of SOI is etched away and that silicon waveguides and membranes remain suspended29,30,31,32. In one notable exception, mechanical motion of thin silicon fin waveguides has been excited by radiation pressure33. Alternatively, stimulated Brillouin scattering has been achieved in regions of chalcogenide glasses that were integrated as part of a passive SOI layout22.

One of the challenges of integrated photonics is the relatively long delay of waveforms, (sometimes referred to as light storage), over tens of ns or longer34. Group delays serve as basic building blocks of discrete-time microwave-photonic filters35 and beam steering modules36,37. Long delays of fast-moving light waves require waveguide paths that are many metres-long. Propagation delays over 100 ns were achieved in long silica or SiN in silica waveguides with ultra-low losses19,38,39, however such optical path lengths cannot be realized in SOI. Waveform delays were also demonstrated in active recirculating loops that were switched on and off by semiconductor optical amplifiers40. Those devices required the hybrid integration of indium-phosphide (InP)-based active layers on top of silica.

The challenge of long time delays of incident analogue waveforms was already faced by electronic integrated circuits more than fifty years ago. A very successful solution path relies on the introduction of surface-acoustic waves (SAWs)41,42,43. Input radio-frequency (RF) waveforms are converted to slow-moving acoustic waves using an array of inter-digital electrodes on top of bonded piezo-electric materials, and recovered back to the electrical domain using a similar, second arrangement41,42,43. The slow speed of sound allows for the realization of delays over physical extents that are five orders of magnitude shorter than electrical paths. So-called SAW devices serve in the filtering, correlation, and analogue processing of RF signals. Advances in high-rate analogue-to-digital conversion and digital signal processing have partially pushed aside SAW-electronic devices. However, ultra-broadband optical signals cannot be digitized directly. Piezo-electric excitation of SAWs in GaAs was previously used in modulation and switching of multiple Mach-Zehnder interferometer waveguides8,9,10.

In this work, we present SAW-photonic devices in standard SOI, which do not require piezo-electric actuation, the suspension of membranes, or the hybrid integration of additional materials. Incident RF waveforms at gigahertz frequencies are converted from the modulation of pump light to the form of surface waves, and then to the modulation of an optical probe that is propagating in a standard photonic circuit. The method of surface waves stimulation is generic and applicable to other substrates as well. Acoustic delays of tens of nanoseconds are achieved on-chip. The SAW-photonic delays are used in four-tap and six-tap discrete-time integrated microwave-photonic filters, with tens of megahertz-wide passbands. The complex weights of individual taps can be designed arbitrarily. The results represent the first introduction and application of opto-mechanics in standard silicon photonics.

## Results

### Principle of operation

The principle of operation of SAW-photonic devices in SOI is illustrated in Fig. 1. A grating of thin gold stripes with period Λ is deposited on an SOI substrate. The grating is illuminated by an optical pump beam, which is amplitude-modulated by a sine wave of radio-frequency f. Absorption of the modulated pump wave leads to periodic temperature changes in the metallic stripes44,45,46. Thermalization of the thin stripes occurs within few picoseconds44,45,46. The temperature perturbations are accompanied by periodic expansion and contraction of the metals, and the resulting strain pattern is transferred to the underlying silicon device layer44,45,46. Strain on the silicon surface is periodic in both space and time, with periods Λ and f, respectively. When the product Λf matches the phase velocity of a surface-acoustic mode of the SOI layer stack, a surface wave may be launched away from the illuminated grating region. The excitation of SAWs through the absorption of short pump pulses in structured metallic patterns has been used on top of bulk silicon wafers44,45,46. Herein, we introduce this technique to integrated photonics.

A standard race-track resonator optical waveguide is defined in the silicon device layer, in proximity to the metallic grating (see Fig. 1). The stimulated SAWs cross the waveguide path in one or more sections. The acoustic waves induce photo-elastic perturbations to the effective index of the optical mode in the resonator waveguide. An optical probe wave, at a frequency within a spectral slope of the resonator transfer function, is coupled into the waveguide. The index perturbation gives rise to intensity modulation of the output probe wave. The incident RF modulation of the optical pump is thereby wavelength-converted onto the probe, via stimulated SAWs.

The principle of operation is analogous to that of traditional SAW-electronic devices, with adaptations to SOI photonics: Piezo-electric transduction and detection are replaced by the absorption of one modulated optical carrier in metal, and the photo-elastic modulation of another in a standard waveguide, respectively. The stimulation of acoustic waves through a given grating strongly depends on the frequency f. Devices therefore function as integrated microwave-photonic bandpass filters32,47,48. Filtering may be enhanced further by multiple crossings of optical waveguide paths with different discrete acoustic delays, as discussed later.

### Experimental results

Figure 2a shows a top-view microscope image of a device under test. A 60 × 60 µm2 grating of gold stripes was patterned 4 µm away from one straight section of a race-track resonator. The grating stripes were defined in parallel with the < 110 > crystalline axis of the silicon device layer. The resonator comprised of ridge waveguides with partial etch depth of 70 nm and 700 nm width. The race-track waveguide was 480-µm-long. The fabrication process is detailed in the Methods. Light was coupled between standard single-mode fibres and the resonator bus waveguide using vertical grating couplers. Coupling losses were 10 dB per facet. Figure 2b shows an optical vector network analyser measurement of the normalized power transfer function of the resonator. The full width at half maximum of the resonant transmission notches is 5 GHz, corresponding to a loaded Q factor of about 40,000. The extinction ratio of the transfer function is ~20 dB.

SAWs were stimulated using an optical pump wave at 1540 nm wavelength (see setup illustration in Fig. 3). The pump wave was amplitude-modulated by a sine wave of variable radio-frequency f from the output port of a vector network analyser. The pump was amplified by an erbium-doped fibre amplifier (EDFA) to an average optical power Ppump between 50 and 500 mW. The end facet of the amplifier’s output fibre was positioned above the gold grating. The vertical separation between the fibre facet and the device plane was adjusted so that the pump beam diameter matched the extent of the grating. An optical probe wave of 1532 nm wavelength and off-chip power of 100 mW was coupled into the resonator waveguide. The probe wavelength was adjusted to match the maximum spectral slope of a transmission resonance. The output probe wave was amplified by another EDFA to an average optical power of 1 mW and detected by a broadband photo-receiver. The detector output voltage was monitored by the input port of the network analyser or by an RF spectrum analyser.

Figure. 4a shows an example of the measured transfer function of RF voltage between the modulation of the incident pump wave and that of the detected output probe wave. The grating period Λ in the device under test was 1.4 µm. A main transmission peak is centred at a frequency of 2.45 ± 0.1 GHz, and a second, weaker peak is observed at 2.85 ± 0.1 GHz. The two frequencies are in good agreement with those of the numerically calculated lowest-order surface-acoustic modes of the SOI layer stack, with a wavelength of 1.4 µm. The calculated spatial profiles of the two modes are shown in Fig. 4b. The full width at half maximum of the primary transmission peak is 200 MHz. The excitation bandwidth is inversely proportional to the number of periods in the grating49, and larger gratings could give rise to narrower spectra. The useful grating size is restricted, however, by acoustic propagation losses (see also below). The magnitude of the output modulation voltage scales linearly with Ppump (Fig. 4c).

Stimulated surface waves pass across two straight parallel waveguide sections within the race-track resonator layout: a first section that is few microns away from the gold grating, and a second section following additional acoustic propagation distance z of 100 µm. The two crossings are illustrated in Fig. 2a. Consequently, the probe wave within the race-track resonator undergoes two photo-elastic perturbation events in each path. Phasor addition of the two events depends on the exact radio-frequency f of the acoustic wave. The transfer function of the device is therefore characterized by interference fringes (see Fig. 4d). The spectral period of the fringes pattern is 35 MHz, in agreement with the acoustic propagation delay of 28.5 ns over the distance z. The propagation losses of acoustic intensity are estimated as 19.5 ± 2.5 dB × mm−1 based on the fringes visibility (see Methods). The losses correspond to an effective propagation length of 225 ± 25 µm. Figure 4d also shows the measured transfer function of the same device following the deposition of a photo-resist on top of the silicon device layer within the race-track perimeter (see image in Fig. 4e). The resist serves as an acoustic absorber, and blocks the SAWs from reaching the second crossing of the race-trace waveguide. The interference fringes visibility is reduced accordingly.

Figure 5a presents the frequencies of the lowest-order peaks in the measured transfer functions for several devices, with different spatial periods Λ of the gold gratings. The frequencies match those of the calculated fundamental surface-acoustic modes of wavelengths Λ. The SAW frequency reaches 8 GHz for Λ = 500 nm (see Fig. 5b). The stimulation method is scalable, in principle, to even higher frequencies, using metal patterns with shorter spatial periods46,50. However, measurements were restricted by the bandwidths of our amplitude modulator, photo-receiver, and network analyser.

The magnitude of photo-elastic perturbations to the effective index of the optical mode in the race-track waveguide was calibrated using the following procedure: the amplitude modulation of the pump wave was switched off, and the input probe wave passed through an electro-optic phase modulator instead (see Fig. 3). The phase modulator was driven by a sine wave at the radio-frequency f of interest. Propagation through the race-track resonator converts the phase modulation of the input probe to intensity modulation at the output. The drive voltage to the phase modulator was varied until the magnitude of output probe modulation equalled that induced by a SAW of the same frequency and a specific Ppump of interest. That value of modulation voltage provides an estimate for the photo-elastic index perturbations magnitude (see Methods for details). The index modulation Δn was 1.2 × 10−6 ± 0.3 × 10−6 refractive index units (RIU) at Ppump of 500 mW (or intensity of about 18 kW × cm−2). The experimental uncertainty corresponds to the standard deviation among the measurements of three devices.

Figure 6 presents the RF power spectrum of the output voltage, obtained for Ppump = 500 mW, f = 2.4094 GHz, and Λ = 1.4 µm. The measurement bandwidth was 10 kHz. RF peak power of −75 dBm (voltage magnitude of 55 µV) is observed at the frequency of stimulation. The DC output voltage was 50 mV. The modulation depth of 0.11% is consistent with the above estimate for Δn (see Methods). The ratio between the peak power and the RF noise power within 1 Hz bandwidth is 70 dB. The signal-to-noise ratio (SNR) may be enhanced with several different schemes (see Discussion below).

Lastly, the layout of the optical resonator waveguide was modified to include four parallel stretches, separated by equal spacing of 40 µm (Fig. 7a). Stimulated SAWs from a 1.4-µm-period gold grating cross the waveguide four times, with a unit differential delay of 10.6 ns between successive events. Figure 7b shows the measured normalized RF power transfer function of the device. The response matches that of a four-tap discrete-time microwave-photonic filter with equal weights. Periodic passbands are observed within the spectral envelope of the SAW stimulation response (see also Fig. 4d). The free spectral range of the filter is 95 MHz, and the full width at half maximum of the passbands is 22 MHz. A device with six crossings and a unit differential delay of 8 ns is shown in Fig. 7c. The device footprint is 200 × 200 µm2. The longest delay difference within that device is 40 ns, corresponding to the optical delay over 8 m of fibre. The measured transfer function is in very good agreement with the design of a six-tap microwave-photonic filter, with a free spectral range of 125 MHz and 20 MHz-wide passbands (Fig. 7d). The results demonstrate the application of SAW-photonic devices in finite-impulse-response, integrated microwave-photonic filters in SOI.

## Discussion

This work presents a first introduction of opto-mechanical interactions and signal processing to standard SOI photonics. The devices do not involve the suspension of membranes or waveguides, and heterogeneous integration of additional material platforms is not required. Light waves propagate in standard ridge waveguides. As an alternative to piezo-electric actuation, SAWs are stimulated through the absorption of pump light in periodic metallic patterns and subsequent thermo-elastic expansion. This method of SAWs stimulation is generic and applicable, in principle, to any substrate. The frequency of the stimulated acoustic waves may be chosen arbitrarily: the excitation of 90 GHz waveforms has been reported in bulk substrates46,50.

The surface waves stimulation principle was previously implemented through the absorption of ultra-short pump pulses in two-dimensional metal structures44,45,46. However, most of the spectral contents of the short pulses do not couple to the acoustic mode. In contrast, we use continuous pump light that is modulated at the radio-frequency of interest. This pumping scheme provides more efficient coupling to the surface wave. The average pump power used in this work is an order of magnitude lower than those of previously used ultra-short pulses44,45,46. In addition, the monitoring of SAWs in previous works had relied on complex free-space measurements of the reflection of an off-plane probe wave44,45,46. Here, photo-elastic modulation of probe waves in planar photonic integrated circuits is used instead.

The concept of SAW-based RF signal processing was successfully carried over from the realm of analogue electronics, where it is known for over 50 years, into integrated photonics. SAWs were successfully used in modulation and switching of photonic circuits in GaAs8,9,10, however the objectives of these works did not include time delay and filtering of RF signals. The delay of microwave signals by 40 ns was realized on-chip within 150 µm (Fig. 7). The delay elements pave the way towards analogue opto-mechanical signal processing in standard SOI. As a first application example, discrete-time integrated microwave-photonic filters with four and six taps, free spectral ranges up to 125 MHz and 20 MHz-wide passbands were demonstrated. The complex weights of individual taps can be chosen arbitrarily, through the exact position, width and curvature of resonator waveguide sections. To the best of our knowledge, the devices represent a first realization of discrete-time microwave-photonic filters based on acoustics.

The photo-elastic index perturbations obtained in this work are comparatively weak: 1.2 × 10−6 RIU for a pump wave intensity of 18 kW × cm−2. The intensity modulation depth of the output probe wave is restricted to 0.1%, and the output SNR over the 20 MHz bandwidth of integrated microwave-photonic filters is presently on the order of unity: a value too low for many signal processing applications. However, the current device metrics do not represent restrictive upper limits on the performance of proposed SAW-photonic concept. Multiple solution paths are available to enhance the output signals by orders of magnitude.

First, the photo-thermal stimulation of SAWs can be made more efficient. The composition and thickness of the metal stripes may be optimized to induce larger strain in the SOI surface. The embedding of the grating stripes within shallow etched patterns in the silicon layer may enhance the SAWs generation51. Concentric metal rings may be used instead of parallel grating stripes to focus the surface waves to a few-microns-size spot, in which the SAW magnitude could be 10-fold stronger7,8,9,10,52. Furthermore, acoustic reflectors can be patterned in the silicon device layer to the sides of the probe resonator waveguide32, to provide feedback cavity enhancement of the surface waves32.

Even for a given SAW magnitude, the intensity modulation depth of the probe wave may be increased significantly. The modulation depth is proportional to the quality factor of the probe wave resonator (see Methods). Devices available to us had a modest loaded quality factor of only 40,000, whereas the state of the art for SOI is ten times better. The modulation depth also scales with the relative fraction of the resonator cavity length that is affected by acoustic waves (see Methods). In present devices, only 60-µm-long sections within a 480-µm-long race-track resonator are perturbed by SAWs. That lengths ratio can be brought close to 100% if the resonator layout is replaced, for example, by a local defect cavity along a Bragg grating in an SOI waveguide52.

Lastly, the output voltage and SNR may also be enhanced even if the modulation depth of the probe wave remains the same. The SNR is currently restricted by the amplified spontaneous emission of the fibre amplifier at the probe wave output path. Optical gain compensates for comparatively large coupling losses of the probe wave in and out of devices: about 10 dB per facet. Coupling losses as low as 2–3 dB per interface are reported in the literature53. Better coupling would provide the same output power with weaker gain, leading to lower amplifier noise. The magnitude of the output voltage signal is presently limited by the maximum power handling of a standard photo-diode. Stronger probe waves may be accommodated using high-power detectors, which are widely employed in microwave-photonics applications32,54.

While the strength of photo-thermal excitation of SAWs would not match that of piezo-electric actuation, future extensions of the proposed concept may well meet the requirements of microwave-photonic signal processing applications. The 200-µm propagation length of 2.5 GHz SAWs in SOI is sufficient for tens of nanoseconds of acoustic group delay, and can accommodate tens of optical waveguide taps in a spiral resonator layout. In addition to potential use in signal processing, the technique is also suitable for studying the acousto-optic properties of materials, and for sensing applications50,52.

In summary, SAW-photonic devices may add another dimension to integrated microwave-photonics, especially in silicon. Building blocks may be brought together with hybrid InP on SOI light sources, silicon-photonic free-carrier modulators and germanium on silicon detectors to form entire systems47,48. Such integration of analogue photonic processing is widely regarded as an enabling technology for next-generation (5G) cellular networks55. Ongoing work is being dedicated to the application of the concept in larger signal processing modules.

## Methods

### Fabrication of devices

Devices were fabricated in standard SOI wafers with a 220-nm-thick silicon device layer on top of a 2-µm-thick buried oxide layer. Gratings of periodic gold stripes were defined by electron-beam lithography, sputtering of a 5-nm-thick chromium adhesion layer followed by 20 nm of gold, and a lift-off process. The sputtering rates for chromium and gold were 0.2 nm × s−1 and 0.5 nm × s−1, respectively. The vacuum level during sputtering was 5 × 10−6 bar and the cycle rate was 5 rpm. Optical waveguides were defined in the silicon device layer using a second phase of electron-beam lithography, followed by inductively coupled plasma reactive-ion etching. Alignment markers were used to define the locations of optical waveguides with respect to the gold gratings. The etching process used a mixture of SF6 and C4F8 gasses, at flow rates of 65 and 10 ccm, respectively. Etching was carried out at a vacuum level of 4 × 10−10 bar, RF power of 100 W and 6 nm × s−1 rate. Ridge waveguides were partially etched to a depth of 70 nm. The width of the ridges was 700 nm. Vertical grating couplers were patterned at the ends of the bus waveguides of race-track resonators. In several devices, 2.5-µm-thick patches of AZ1518 photo-resist were patterned inside the race-track perimeter through photo-lithography. The resist patches served as acoustic absorbers.

### Estimate of surface-acoustic waves propagation losses

Consider SAWs that are stimulated in a metallic grating adjacent to a ring resonator, as shown in Fig. 2a. The surface waves first path through one straight section of the race-track layout, introducing photo-elastic index perturbations of magnitude Δn. Following a propagation distance z = 100 µm, the SAWs cross a second straight section of the resonator (Fig. 2a). The magnitude of photo-elastic perturbation in that second waveguide segment is $$\Delta n\exp \left( { - \alpha _{{\mathrm{SAW}}}z/2} \right)$$, where αSAW denotes the propagation losses coefficient of SAWs intensity in units of m−1. Perturbations in both sections contribute to intensity modulation of the output probe wave. Their addition is constructive (destructive) when the propagation distance z is an even (odd) integer multiple of half the surface-acoustic wavelength. The transfer function of the device is therefore characterized by a fringes pattern (see Fig. 4d). The fringes visibility is given by $$\left[ {1 + \exp \left( { - \alpha _{{\mathrm{SAW}}}z/2} \right)} \right]/\left[ {1 - \exp \left( { - \alpha _{{\mathrm{SAW}}}z/2} \right)} \right]$$. The measured visibility of 4 ± 0.5 corresponds to αSAW = 19.5 ± 2.5 dB × mm−1.

### Calibration of photo-elastic index perturbation magnitude

Let us denote the instantaneous photo-elastic perturbation to the effective modal index of the race-track resonator waveguide as Δn(f)sin(2πft), where f is the radio-frequency of a SAW and t stands for time. The index perturbations induce periodic variations in the single-path phase delay of a probe wave within the resonator: Δφ = k0l Δn(f)sin(2πft). Here k0 is the vacuum wavenumber of the probe wave and l denotes the length of the waveguide section that is affected by the SAW, which approximately equals the length of the stripes in the gold grating.

The variations in the optical phase delay introduce oscillating spectral shifts in the transfer function of the resonator, with respect to the fixed optical frequency of the probe wave. For example, phase delay variations of 2π correspond to a spectral offset by a single free spectral range: c/(nL), where c is the speed of light in vacuum, n denotes the group index of the race-track waveguide, and L is the race-track length. SAWs introduce phase variations Δφ that are much smaller than 2π. The magnitude of spectral shifts in the transfer function is given by:

$$\Delta \nu _{{\mathrm{SAW}}}\left( f \right) = \frac{{k_0l \cdot \Delta n\left( f \right)}}{{2\pi }}\frac{c}{{nL}} = \nu _0\frac{l}{L}\frac{{\Delta n\left( f \right)}}{n}.$$
(1)

Here ν0 stands for the fixed optical frequency of the probe wave (~193 THz), which is chosen on a spectral slope of the resonator transfer function. The spectral frequency shifts of the resonator response manifest in amplitude modulation of the output probe.

In order to calibrate the magnitude of index perturbations, auxiliary measurements were carried out with the intensity modulation of the pump wave switched off. Instead, the probe wave at the input end of the race-track resonator passed through an electro-optic phase modulator (see Fig. 3). The phase modulator was driven by a sine wave voltage at radio-frequency f and magnitude VPM(f). The phase modulation corresponds to periodic shifts in the instantaneous optical frequency ν(t):

$$\nu \left( t \right) = \nu _0 + {\mathrm{\pi }}\frac{{V_{{\mathrm{PM}}}\left( f \right)}}{{V_{\mathrm{\pi }}}}f \cdot \cos \left( {2{\mathrm{\pi }}ft} \right) = \nu _0 + \Delta \nu _{{\mathrm{PM}}}\left( f \right) \cdot \cos \left( {2{\mathrm{\pi }}ft} \right).$$
(2)

Here we denote the magnitude of the frequency modulation of the probe wave as $$\Delta \nu _{{\mathrm{PM}}}\left( f \right) \equiv {\mathrm{\pi }}fV_{{\mathrm{PM}}}\left( f \right)/V_{\mathrm{\pi }}$$, and Vπ ~ 3.5 V is the voltage required for an electro-optic phase shift of π radians. Similar to the photo-elastic perturbations discussed above, the frequency modulation of the input probe wave is converted to intensity modulation at the output end. Here, however, the instantaneous optical frequency of the probe is shifting with respect to a stationary resonator response, rather than the other way around.

In the experiment, VPM(f) is modified until the voltage modulation of the detected output probe matches the level previously measured for SAWs at the pump power of interest. Both measurements are taken for the same ν0 and the same probe power. Matching between the magnitudes of the output voltage modulation in the two cases signifies ΔνPM(f) = ΔνSAW(f), leading to the following estimate for the photo-elastic index perturbations magnitude:

$$\frac{{\Delta n\left( f \right)}}{n} = {\mathrm{\pi }}\frac{{V_{{\mathrm{PM}}}\left( f \right)}}{{V_{\mathrm{\pi }}}}\frac{f}{{\nu _0}}\frac{L}{l}.$$
(3)

### Modulation depth of the output probe

The conversion of photo-elastic index perturbation to probe intensity modulation is determined by the spectral slope of the resonator power transfer function T(ν0). The exact value of the derivative ∂T(ν0)/∂ν0 depends on the precise tuning of ν0. However, for a resonator close to critical coupling, we may approximate $$\partial T\left( {\nu _0} \right)/\partial \nu _0 \approx 1/\Delta \nu _{{\mathrm{FWHM}}}$$ where ΔνFWHM is the full width at half maximum of T(ν0). Using Eq. (1), we obtain an estimate for the magnitude ΔPpr(f) of the modulation of the probe output power:

$$\frac{{\Delta P_{\Pr }\left( f \right)}}{{P_{\Pr }}} \approx \frac{{\Delta \nu _{{\mathrm{SAW}}}\left( f \right)}}{{\Delta \nu _{{\mathrm{FWHM}}}}} = \frac{{\Delta n\left( f \right)}}{n}\frac{l}{L}\frac{{\nu _0}}{{\Delta \nu _{{\mathrm{FWHM}}}}} = \frac{{\Delta n\left( f \right)}}{n}\frac{l}{L}Q.$$
(4)

Here Q is the loaded quality factor of the race-track resonator and Ppr denotes the average output power of the probe wave. For the parameters of this work: Q ~ 40,000, L = 480 µm, l ~ 60 µm, n = 3.5 RIU and Δn ~ 1.2 × 10−6 RIU, the modulation depth ΔPpr(f)/Ppr of the output probe is expected to be on the order of 0.17%. This estimate is in agreement with measurements.

## Data availability

The source data underlying Figs. 2b, 4a, c, d, 5a, b, 6, 7b, d are provided as a Source Data file.

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## Acknowledgements

This work was supported in part by a Starter Grant from the European Research Council (ERC), grant number H2020-ERC-2015-STG 679228 (L-SID).

## Author information

Authors

### Contributions

D.M. designed the devices and performed simulations. M.K. and M.H. led the fabrication efforts. D.M. and M.K. performed the optical and acousto-optic characterization of devices. M.P., M.F., and T.S. participated in the fabrication of devices. M.H. and M.P. carried out the microscopy analysis of devices. S.L. proposed the photo-elastic modulation of resonator waveguides. A.B. assisted with the assembly of the measurement setup and the literature survey. A.Z. proposed the concept of surface-acoustic waves-photonics in silicon on insulator, managed the project, and wrote the paper.

## Ethics declarations

### Competing interests

The authors declare no competing interests.

Peer Review Information Nature Communications thanks Jose Azana and other, anonymous, reviewer(s) for their connotestribution to the peer review of this work. Peer reviewer reports are available.

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Munk, D., Katzman, M., Hen, M. et al. Surface acoustic wave photonic devices in silicon on insulator. Nat Commun 10, 4214 (2019). https://doi.org/10.1038/s41467-019-12157-x

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• DOI: https://doi.org/10.1038/s41467-019-12157-x

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